AU612823B2 - Creación de Inventos y Patentes con Inteligencia Artificial

AU612823B2 – Edge effect reduction by smoothing in digital receivers
– Google Patents

AU612823B2 – Edge effect reduction by smoothing in digital receivers
– Google Patents
Edge effect reduction by smoothing in digital receivers

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Publication number
AU612823B2

AU612823B2
AU33163/89A
AU3316389A
AU612823B2
AU 612823 B2
AU612823 B2
AU 612823B2
AU 33163/89 A
AU33163/89 A
AU 33163/89A
AU 3316389 A
AU3316389 A
AU 3316389A
AU 612823 B2
AU612823 B2
AU 612823B2
Authority
AU
Australia
Prior art keywords
edge
signal
smoothing
data
frequency
Prior art date
1988-04-22
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)

Ceased

Application number
AU33163/89A
Other versions

AU3316389A
(en

Inventor
Kapriel V. Krikorian
Robert A. Rosen
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)

Raytheon Co

Original Assignee
Hughes Aircraft Co
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
1988-04-22
Filing date
1989-04-18
Publication date
1991-07-18

1989-04-18
Application filed by Hughes Aircraft Co
filed
Critical
Hughes Aircraft Co

1989-10-26
Publication of AU3316389A
publication
Critical
patent/AU3316389A/en

1991-07-18
Application granted
granted
Critical

1991-07-18
Publication of AU612823B2
publication
Critical
patent/AU612823B2/en

2009-04-18
Anticipated expiration
legal-status
Critical

Status
Ceased
legal-status
Critical
Current

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Classifications

H—ELECTRICITY

H03—ELECTRONIC CIRCUITRY

H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS

H03H17/00—Networks using digital techniques

H03H17/02—Frequency selective networks

Description

r. r COMMONWEALTH OF AUSTRALIA PATENTS ACT 1952 Fol COMPLETE SPECIFICAT FOR OFFICE USE Short Title: Int. Cl: Application Number: Lodged: Complete Specification-Lodged: Accepted: Lapsed: Published: Priority: Related Art: TO BE COMPLETED BY APPLICANT Name of Applicant: Address of Applicant: Actual Inventor: Address for Service: HUGHES AIRCRAFT COMPANY 7200 Hughes Terrace, Los Angeles, CALIFORNIA 90045-0066, U.S.A.
Robert A. Rosen and Kapriel A. Krikorian 4 GRIFFITH HACK CO.
71 YORK STREET SYDNEY NSW 2000
AUSTRALIA
Complete Specification for the invention entitled: EDGE EFFECT REDUCTION BY SMOOTHING IN DIGITAL RECEIVERS 18/04 /89 -_.00685′ The following statement is a full description of this invention, including the best method of performing it known to me/us:- 0073A:rk
^I_
1P- EDGE EFFECT REDUCTION BY SMOOTHING IN DIGITAL RECEIVERS BACKGROUND OF THE INVENTION 1 1. Freld of the Invention This invention relates to methods and apparatus for improved detection, analysis, and discrimination of signals in receiving devices. In particular, these methods and apparatus reduce the undesirable effects of sharp signal pulses, called edges, from strong signal emitters, allowing for greater dynamic ranges in detection.
2. Background of the Invention Devices which receive and analyze a plurality of o 0 incoming signals through one or more detectors ofE+n process S0 these signals to determine the number, direction, and strengths of various signal emitters within their vicinity.
Radar and sonar receivers provide good examples of such detection devices. These receivers seek to locate and #8 15 identify all emitters in their area, including both strong and weak signal sources. However, certain obstacles prevent precise and complete tracking. In particular, signals which turn suddenly on or off during reception anl I processing tend to drown out weaker signals, making their detection and discrimination much more difficult.
Many signal detection devices rely upon spectral analysis to identify and discriminate among a plurality of radar, sonar, or other electromagnetic signal sources. For -tl i ~l .i_ 2 1 data in digital form, spectral analysis through the use of a Fast Fourier Transform (FFT) yields the frequency spectrum which a particular signal source emits, effectively tagging individual sources by their frequencies. Fourier theory shows that any arbitrary signal or function, in this case a function of time, namely an electromagnetic wave, can be broken down or decomposed into a sum of individual sine waves oi differing frequency.
The results of an FFT are often expressed in a power spectrum chart, graphing the amplitude weighting for each fourier sine wave component as a function of that component’s frequency (sometimes called a frequency bin or an FFT «filter»). One can reconstruct the original repeating signal function by multiplying each sine wave by its amplitude in the power spectrum and adding the resulting products. An FFT of a simple sine wave yie2L] a single amplitude point on a power spectrum, at ex, ctly that frequency. For an arbitrary signal in time, the power spectrum will generally be more complex, but will have a peak centered on the emitter’s principal frequency.
Fourier transform theory assumes that the signal 0 being analyzed has been «on» forever. If a signal that 0 appears to be a clean repeating sine wave suddenly turns off or on during an FFT analysis, the power spectrum no longer provides a simple answer for the emitter frequency. This sudden turning on or off during transmission defines a I I i i-.ilx;-.
3 1 signal «edge». The power spectrum of an edge no longer yields a peak for a single frequency. Instead, one requires an infinite number of sine wave frequencies to reconstruct the sudden discontinuity in the repeating wave. Hence, a power spectrum of an edge gives rather large amplitudes for a continuum of temporal frequencies. This broadened power spectrum constitutes a «spectral splatter» for the signal being analyzed. Such frequency or spectral splatter impairs detection of weaker radar signals, simply because the frequency components of the edge drown out a signal of weaker frequency. No method or apparatus has been available to reduce the spectral splatter of an edge, while still o detecting the primary frequency of the strong emitter and also detecting the frequency of weaker signals.
02″I5 SUMMARY OF THE INVENTION This invention provides methods and apparatus for reducing spectral splatter produced in a digital receiver 0 due to receiving edges from strong signal emitters. These apparatus include means for digitizing and buffering incoming signal data. In preferred embodiments, this data includes a plurality of signals of different frequency and comprising complex-valued numbers. Along a separate path, these apparatus provide means for ascertaining the presence of one or more edges in the same digitized data. If an edge occurs, special values or sets of weights are applied to the buffered data which smooth out the discontinuity in i ra~ 1. the edge. When the smoothed out edge is processed by the spectral analysis Fast Fourier Transform (FFT) stage, spectral splatter is reduced or eliminated. The result is that the frequency spread caused by the edge is quenched, and the signal-to-noise ratios for signals of other, and especially weaker, frequencies are increased. In other words, the strong edge and spectral splatter associated with a signal of a given frequency no longer drowns out weaker signals at other frequencies.
DESCRIPTION OF THE DRAWINGS The invention may be better understood through reference to the following figures: FIG. 1 represents a block diagram of the flow of data in the present invention.
FIGS. 2A and 2B show graphs of a strong signal over time and its corresponding Fourier power spectrum, with a superimposed weaker signal.
FIGS. 3A, 3B, and 3C show graphs of a strong signal over time with a pulse edge and the corresponding Fourier power spectrums both with and without edge smoothing.
a DESCRIPTION OF A PREFERRED EMBODIMENT FIG. 1 shows a block diagram for a digital radar receiver. The Analog-Digital Conversion (ADC) Block 12 receives and converts analog data 10 to digital information.
The data is duplicated after this point, with one set of r- I rlrr~i 1 data delayed in a buffer 14 while the other set travels through the Edge Detection processing blocks 16 and 18.
Within this path, the Magnitude Detection Block 16 forms real magnitudes out of the ADC complex number outputs, for use in recognizing edges. The real magnitude may be formed from the complex numbers in an approximate way, by taking (if the data is given by a bi) the real value as Max[ial,|b|] 1/2 Min[ |aj, in order to save processing time. The real magnitude values for each signal are then sent to the Edge Detection block 18.
The Edge Detection Block 18 determines whether an i iedge is present or not. It performs this function in two stages. First, for each point j in the signal or data stream, clusters of data points located at some time n before the point are subtracted from clusters of data points located at some time n after the point. Thus, if some discontinuity should occur, subtracting points before and after the discontinuity would yield an offset.
After taking the positive value of the offset bj for the given point, it is compared with the offset values immediately before (bjl) and immediately after (bj+l) the point in question. If the offset is larger than either of its neighbors and is larger than a threshold determined from the data itself, then an edge is declared at point j.
In the Edge Detection Block 18, if individual input amplitude magnitudes are given by aj, where j denotes
L
6 1 the sequential order of the pulses and hence their time of arrival, then weighted offset values bj can be calculated as follows: mem maj n+i i=-m oo a o 0 a 0 0 0 0 0 0 0 0..15 o 0 i oaa 00 4 0 00 0 0 e00e 0 a 0 0 0 0 00000 0 a0 6 a. o The summation bounds m and the offset n can be determined for particular applications to yield the most efficient process timesaving) and accurate algorithm required.
The resulting weighted values bj for each data point j can be used to detect a pulse edge.
As described, a pulse edge is declared if bj >bj+ 1 and bj bj-1 and bj tj, i.e. if bj is greater than its nearest neighbors and is greater than some threshold value determined by m m tj S Min aj+n+i, j-n+i i=-m i=-m i 1 7 1 where parameter S determines the relative sensitivity for thresholding sharp edges. «Min» refers to taking the value of the minimum of the arguments within the brackets.
Configuring the parameters used in the algorithms requires testing sample data and varying the parameters, m,n, and S until the best results are obtained, best meaning the lowest overall frequency noise from sharp edges. The algorithm described for determining the bj’s and for declaring pulse edges is just one example of various processing alternatives.
As a processing time saver, the partial summation results used for every jth data point as shown above can be kept in memory and updated easily for each incoming data point by adding and subtracting the data points in a buffer.
This partial summing can save processing time.
Once the Edge Detection Block 18 determines an edge through the above procedure, it sends an instruction to the Pulse Smoothing block 20 to apply the smoothin weights to the data’s edge. Using one method, the weights are applied by multiplying a set number of the samples around the edge at sample j by a fixed weight set centered on data sample j.
The weighting algorithm can be varied for specific system goals, requiring a tailoring of the weights to the particular data, their dynamic range, and to the FFT i- _C -L L.I 1 algorithms being used. As a preferred embodiment, the weighting used is represented by Ws(t), given by: (1 cos[2 /N fs(t-T)] W for tfs(t-t) N/2 elsewhere where fs is the data sampling rate and N is the number of samples weighted. TC is the pulse rise time. The smoothing of the sharp discontinuity, or edge, reduces the spectral splatter or interchannel noise in the resulting power spectrum as described before.
After any necessary edge-smoothing weights are applied to the edges, normal pre-FFT amplitude weights 22 are applied (for example Dolph-Chebyshev weights) which reduce sidelobes for the FFT being used. An FFT normally processes a set number of data points at a time, the number of data points used being called the «window». If the FFT window doesn’t quite match the weighted data stream, some S data turning 22 may be required to properly match the weighted sample size to the FFT window. As an alternative to the edge smoothing approach described, a whole collection of possible weights could be preset and used depending on the location of the edge within the FFT processing window.
9 1 This can save processing time by calculating in advance all possible weighting combinations. In a further variation of this approach, the edge smoothing weights and the single set of amplitude (Dolph-Chebyshev) weights are replaced by a group of combined weights, each pre-optimized for a particular location of the pulse edge within the FFT processing window.
The two approaches discussed have benefits and drawbacks. The first approach, multiplying when detected each edge by the weights, has the greater flexibility. Any number of edges within a given window can be smoothed, and modularity allows different post-processing to be done without reprogramming or restructuring the smoothing step.
The second approach, having preset weighting sets, 15 implements the edge smoothing into a total processing system, trading flexibility for processing speed and preoptimization.
After the spectral analysis FFT step represented by block 24 is performed, magnitude detection, noise estimation, thresholding, derivation of pulse descriptors, and the final emitter classifications and identifications are made.
Magnitude detection, after the FFT is performed, determines tne strengths of each frequency given in the filters of the FFT. Each filter bin represents a possible signal and its relative strength determines how likely it is i m I fI 1 an actual signal from an existing emitter. The noise estimation stage determines the noise level of all the filter bins in order to form a reasonable thresholding value for removing noise from true signals. The removal process is performed at the thresholding stage, using the threshold already determined.
Once a collection of signals is obtained, the pulse descriptor stage calculates the angle and times of arrival of given frequency signals, their pulse widths and their amplitudes or strengths. Determining the angle of an emitter often requires a plurality of antennas or detectors to triangulate the signal source. On the basis of these descriptors, time histories of pulses are created in the classification and identification stage, so that received 15 pulses are correlated with emitters and these emitters may be tracked in time.
0FIGS 2 and 3 illustrate a simple operation of the S present invention. FIG. 2A reveals a strong signal sine wave 102, graphed with its amplitude A over time t. FIG. 2B shows the power spectrum resulting from performing an FFT upon the strong signal. F(f) represents the relative strength of the incoming signals versus frequency. The tall bin 104 is the amplitude of the strong signal; smaller bin 106 represents a relatively weak signal detected along with the stronger signal. In this case, both signals are easy to detect and distinguish from one another.
I
11 1 FIG. 3A represents the same strong signal 202 as FIG. 2A but here the signal suddenly cuts off at time t designated to. A dashed line 203 indicates the smoothing of the discontinuity which the present invention provides.
FIG. 3B shows a power spectrum of the strong signal and its edge without any smoothing, having every FFT filter or bin excited. The noise or spectral splatter resulting from the signal edge washes out the small signal 206 shown by the, dotted lines. FIG. 3C shows the power spectrum resulting after edge smoothing, the noise being much smaller in strength. One clearly discerns the strong frequency 304 as well as the weaker frequency signal 306. Edge smoothing greatly reduces the FFT noise or spectral splatter, allowing detection of smaller signals and thereby increasing the dynamic range for detection.

AU33163/89A
1988-04-22
1989-04-18
Edge effect reduction by smoothing in digital receivers

Ceased

AU612823B2
(en)

Applications Claiming Priority (2)

Application Number
Priority Date
Filing Date
Title

US185018

1988-04-22

US07/185,018

US4958361A
(en)

1988-04-22
1988-04-22
Edge effect reduction by smoothing in digital receivers

Publications (2)

Publication Number
Publication Date

AU3316389A

AU3316389A
(en)

1989-10-26

AU612823B2
true

AU612823B2
(en)

1991-07-18

Family
ID=22679214
Family Applications (1)

Application Number
Title
Priority Date
Filing Date

AU33163/89A
Ceased

AU612823B2
(en)

1988-04-22
1989-04-18
Edge effect reduction by smoothing in digital receivers

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US
(1)

US4958361A
(en)

EP
(1)

EP0343370B1
(en)

AU
(1)

AU612823B2
(en)

CA
(1)

CA1319959C
(en)

DE
(1)

DE68917641T2
(en)

ES
(1)

ES2058376T3
(en)

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Assignee
Title

US4984253A
(en)

1988-06-03
1991-01-08
Hughes Aircraft Company
Apparatus and method for processing simultaneous radio frequency signals

US5216696A
(en)

1989-12-22
1993-06-01
Comsat Laboratories
Programmable noise bandwidth reduction by means of digital averaging

JP2768548B2
(en)

1990-11-09
1998-06-25
シャープ株式会社

Panel display device

US5367539A
(en)

1991-12-31
1994-11-22
At&T Bell Laboratories
Digital block processor for processing a plurality of transmission channels in a wireless radiotelephony system

US5381150A
(en)

1993-05-07
1995-01-10
Trw Inc.
Partial intercept LPI (low probability of intercept) reconnaissance system

US6249796B1
(en)

1998-12-08
2001-06-19
Siemens Medical Systems, Inc.
Real-time technique for reducing the settling time of a high pass filter

US6515527B2
(en)

2001-06-22
2003-02-04
Sun Microsystems, Inc.
Method for smoothing dI/dT noise due to clock transitions

CN102841336A
(en)

2012-09-04
2012-12-26
中船重工鹏力（南京）大气海洋信息系统有限公司
High-frequency ground wave radar multi-frequency signal coherent receiver

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Publication date
Assignee
Title

GB1448697A
(en)

1973-09-25
1976-09-08
Post Office
Non-linear correction of waveforms

US4358788A
(en)

1981-02-27
1982-11-09
Rca Corporation
Legibility for alpha-mosaic characters

US4410955A
(en)

1981-03-30
1983-10-18
Motorola, Inc.
Method and apparatus for digital shaping of a digital data stream

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(en)

1981-12-31
1988-09-22
Secr Defence Brit
Receivers for navigation satellite systems

JPH055725Y2
(en)

1987-02-06
1993-02-15

1988

1988-04-22
US
US07/185,018
patent/US4958361A/en
not_active
Expired – Lifetime

1989

1989-04-18
DE
DE68917641T
patent/DE68917641T2/en
not_active
Expired – Fee Related

1989-04-18
AU
AU33163/89A
patent/AU612823B2/en
not_active
Ceased

1989-04-18
EP
EP89106901A
patent/EP0343370B1/en
not_active
Expired – Lifetime

1989-04-18
ES
ES89106901T
patent/ES2058376T3/en
not_active
Expired – Lifetime

1989-04-21
CA
CA000597456A
patent/CA1319959C/en
not_active
Expired – Fee Related

Also Published As

Publication number
Publication date

CA1319959C
(en)

1993-07-06

ES2058376T3
(en)

1994-11-01

EP0343370A3
(en)

1990-09-19

EP0343370B1
(en)

1994-08-24

DE68917641T2
(en)

1995-04-13

DE68917641D1
(en)

1994-09-29

US4958361A
(en)

1990-09-18

AU3316389A
(en)

1989-10-26

EP0343370A2
(en)

1989-11-29

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