GB1568691A - Creación de Inventos y Patentes con Inteligencia Artificial

GB1568691A – Electronic filter circuit
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GB1568691A – Electronic filter circuit
– Google Patents
Electronic filter circuit

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Publication number
GB1568691A

GB1568691A
GB43843/76A
GB4384376A
GB1568691A
GB 1568691 A
GB1568691 A
GB 1568691A
GB 43843/76 A
GB43843/76 A
GB 43843/76A
GB 4384376 A
GB4384376 A
GB 4384376A
GB 1568691 A
GB1568691 A
GB 1568691A
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United Kingdom
Prior art keywords
terminal
network
filter
operational amplifier
capacitor
Prior art date
1975-11-03
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GB43843/76A
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Sundstrand Data Control Inc

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Sundstrand Data Control Inc
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1975-11-03
Filing date
1976-10-22
Publication date
1980-06-04

1976-10-22
Application filed by Sundstrand Data Control Inc
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Sundstrand Data Control Inc

1980-06-04
Publication of GB1568691A
publication
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patent/GB1568691A/en

Status
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legal-status
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Classifications

H—ELECTRICITY

H03—ELECTRONIC CIRCUITRY

H03H—IMPEDANCE NETWORKS, e.g. RESONANT CIRCUITS; RESONATORS

H03H11/00—Networks using active elements

H03H11/02—Multiple-port networks

H03H11/04—Frequency selective two-port networks

H03H11/12—Frequency selective two-port networks using amplifiers with feedback

H03H11/126—Frequency selective two-port networks using amplifiers with feedback using a single operational amplifier

Description

PATENT SPECIFICA Ti ON («) 1 568 691
_ 1 ( 21) Application No 43843/76 ( 22) Filed 22 Oct 1976 ( 31) Convention Application No 624806 ( 19) ( 32) Filed 3 Nov 1975 in ( 33) United States of America (US) ( 44) Complete Specification published 4 June 1980 ( 51) INT CL’ H 03 H 5/02 ( 52) Index at acceptance H 3 U SOD ( 54) ELECTRONIC FILTER CIRCUIT ( 71) We, SUNDSTRAND DATA CONTROL INC, a Corporation organised and existing under the laws of the State of Delaware, United States of America, of Overlake Industrial Park, Redmond, Washington, United States of America, do hereby declare the invention, for which we pray that a patent may be granted to us, and the method by which it is to be performed, to be particularly 5
described in and by the following statement:-
The invention relates to the field of electronic signal filters and more particularly to the field of active shunt, low pass filters.
There are many applications where it is considered highly desirable to permit low frequency signals including a DC current to flow through the filter and at the same 10 time to provide for rapid attenuation of the signal above a predetermined, or break frequency For example, in accelerometers it is desirable to pass, with as little attenuation as possible, the DC or low frequency output of the accelerometer while at the same time filtering out higher frequency signals that may be generated by vibration or the like 15 In addition to having demanding frequency response characteristics, the use ot filters with accelerometers requires that the physical dimensions of the filter be as small as possible since they are quite often used in applications where weight and space are critical such as missile guidance systems Therefore, in addition to providing the desired operational characteristics, it is considered highly desirable 20 to reduce the actual physical size and weight of the filter components to a minimum These size and weight considerations tend to rule out purely passive filters due to the fact that they require one or more inductors which, of course, add weight and size along with generally increased cost Besides being smaller and lighter, active elements generally provide more in the way of design flexibility and 25 better frequency response than filters constructed out of only passive elements, since an active RC network can result in a filter with natural frequencies anywhere in the left half of the complex frequency plane It is also considered desirable to reduce the number of stages required for a particular order of operation In many of the prior art active filters, such as Morris U S Patent No 3,122,714, it is 30 necessary to cascade a number of filter stages to get a higher order of operation.
The invention relates to n-order active shunt filters, by which is meant 2terminal networks which are connected in use as a shunt across a signal path, and have an nth order voltage/current ratio The invention provides such an norder active shunt filter, being a two-terminal network for passing a shunt filter current 35 through the network when an input signal from a signal source is applied to the terminals; the filter comprising an n-1 order active network (as defined below) having an input terminal connected to a first terminal of the 2-terminal network, a reference terminal connected to the second terminal of the 2-terminal network, and an output terminal; and a capacitor C operatively connected between the first 40 terminal of the 2-terminal network and the output terminal of the active network, wherein the shunt filter current is through the capacitor C.
By an n-l order active network there is meant an active network having an n-1 order voltage transfer function.
The use of an n-1 order active network in conjunction with a capacitor to 45 provide an n-order filter is demonstrated mathematically below, and is advantageous in that the number of components in the active network is reduced over the number that would otherwise be used if an n-order active network were utilized The filter is described as a shunt filter because it performs its filtering by means of a shunt current through the capacitor C The filter is described as an «active» shunt filter because the shunt filter current is controlled by filter elements of the active network.
The filter of the invention can be designed as a low pass filter without the necessity of cascading separate filter stages It can be designed as any norder, from 5 a filter order (n=l) filter upwards.
The invention also provides such an n-order active shunt filter in which the n-1 order active network comprises a differentiating circuit operatively connected to one of the terminals and an n-2 order active network operatively connected to the differentiating circuit 10 The filter responds to an input signal, either from a voltage source or current source, applied to the input terminals Connected across the input terminals is the n 1 active network containing an active element such as an operational amplifier.
Advantageously the input impedance to the active network is maintained at a very high level so that the current actually flowing into the active network, and thus its 15 effect on the output of the filter, is minimized The capacitor C connects the output of the active network to the output of the filter The active network responds to the input signal in such a manner as to generate across the capacitor C a voltage which results in a shunt current flowing from the output of the filter through the active network, thereby providing the desired filter characteristics By adjusting the value 20 of the transfer function of the active network (as herein defined), the voltage across the capacitor C, and hence the size of the capacitor C, can be adjusted in order to provide the desired shunt current.
As a result, it is possible to produce an n-order filter having a single stage which will have essentially any order response desired and since an n-1 active 25 network is utilized, the number of components in the active network is reduced In addition, by increasing the voltage output of the active network, the size of the capacitor C required to produce the same shunt current is reduced, thus making it possible further to reduce the physical dimensions of the filter.
Under certain circumstances the selection of the capacitor along with other 30 filter elements having certain predetermined relationships to the active network’s transfer function makes it possible to achieve n-order filter characteristics by utilizing an n-2 order active network in combination with a differentiating element.
This approach significantly reduces the synthesis problems in designing practical filters 35 This approach to low pass filter design provides two major advantages: first, the active portion of the filter is designed with at least one less order of operation, n-l, with the concomitant reduction in the active network components; and secondly, the physical size of the capacitor C may be reduced by increasing the voltage output of the active network, thus reducing the physical dimensions of the 40 filter.
The invention is hereinafter particularly described, by way of example only, with reference to the drawings of which:
Figure 1 is a block diagram of an n-order active shunt low pass filter; Figure 2 is a schematic diagram of a first order shunt filter wherein the load 45 impedance Z of Figure 1 is equal to a simple resistance R,; Figure 3 is a schematic diagram of a second order shunt filter wherein the load impedance Z of Figure 1 is equal to a simple resistance R,; Figure 4 is a block diagram of the n-order active shunt filter of Figure 1 wherein the load impedance Z is a resistor R, and a capacitor C, connected in 50 parallel; Figure 5 is a schematic diagram of a second order shunt filter of the type in Figure 4; Figure 6 is a schematic diagram of a second order shunt filter of the type in Figure 4 wherein a differentiating element is used in combination with an n-2 55 active network; Figure 7 is a schematic diagram of a third order shunt filter of the type in Figure 4 wherein a differentiating element is used in combination with an n-2 active network:
Figure 8 is a schematic diagram of a third order shunt filter of the type in 60 Figure 4 wherein a virtual ground concept is used; Figure 9 is a block diagram of the shunt filter of Figure 1 with a voltage source for input; and Figure 10 is a block diagram of the shunt filter of Figure 1 with a current output 65 1,568,691 3 1,568 691 3 In the block diagram of Figure 1 an n-order, low pass filter is illustrated in conjunction with a current source utilized for signal input The input signal source, in this case a current source, is indicated within the dashed line 10, and, for example, could represent the signal output of an accelerometer In the signal source 10, a portion I, of the current IT is shunted through a load impedance Z An 5 active network 12 receives its input from the current source 10 by means of a line 14 and in order to maintain the actual current I, through line 14 as small as possible, the input impedance of the active network 12 is very high The active network 12 is also connected to the lower portion of the filter, represented by a line 13, by means of a line 16 Normally, the lower portion 13 of the filter will be maintained at a 10 reference or ground potential Output of the active network 12 is connected to the output of the filter by means of a capacitor C inserted in line 18 The basic filter operation is thus provided by a shunt current I, flowing through line 18 and line 16 wherein the actual magnitude of Is is a function of the size of the capacitor C and the voltage EA produced by the active network 12 The relationship between the 15 output voltage of the filter E and EA is governed by the transfer function G of the active network 12, where G=E,/E O Thus, the desired filter is obtained by utilizing an active network 12 having a transfer function G that generates the voltage EA, which in combination with capacitor C, results in a shunt current I%, thereby providing a filter having an n-order response 20 The transfer function G of the n-l active network 12 resulting in an norder filter having the desired characteristics is represented by the equation:
E =_ = _ 1 F|D 1 15 E A _ ( 1) E O CS l 1 ‘L L where: S represents the Laplace operator; R, represents the real portion of the impedance Z at DC; and D defines that portion of the filter characteristic which 25 can be represented by a Laplace filter polynomial:
D=A,’Sn+^,Sn-‘+ +AS+l where A,, A 1,- A represent the filter polynomial coefficients.
The transfer function G represented by equation ( 1) can be derived from the following relationships inherent in the circuit of Figure 1 The output signal E of 30 the filter is represented by the equation:
ITR, ITR, E O ( 2) An Sn+An,Sn-,+ +AS+ 1 D where ITRL serves to define the DC characteristics of the filter output signal E and D defines the AC characteristics of the output signal E Because the current I, is, as stated above, kept as small as possible its effect on the circuit can be ignored 35 Thus E is equal to ILZ, or (IT-Is)ZL, and the shunt current Is can be represented as:
S ZLD l T by combining EO=(IT-Is)ZL with equation ( 2) Here the shunt current Is across the capacitor C of Figure 1 can also be represented as:
I%=(E 0-E)CS ( 4) 40 and by substituting equation ( 4) into equation ( 3) as such:
S j i LDlL D (EO EA) CS ( 5) 4 1,568,691 4 E lD _ 1 C 51 = EACS ( 6) the basic transfer equation ( 1) of the active network 12 in Figure 1 results, i e.
G = l A = 1 lRL 1 _ c E 0 CS lRL Cs (I) It should be understood that the active network transfer function G depends in any practical filter on the nature of the impedance Z Taking, for example, as a 5 first special case, a filter where Z is equal to the simple resistance R,, the transfer function G of equation ( 1) is equal to:
G = EA 1 FD 1 C Sl ( 7) io RLCS lL since RL is merely substituted for ZL in equation ( 1) In this case, by replacing D with the filter polynomial, the transfer function equation ( 7) becomes: 10 = l A-RLC lA _ sn-1 + An 1 Sn-2 + S+ LRLCJ LAA-RLC A-RLC A-RLC J ( 8) Inspection of the transfer function equation ( 8)G reveals that it is only necessary to synthesize an n-1 order network to produce an n-order filter.
Along with reducing the number of components, in the active network the requirement of only synthesizing an n-1 order network substantially reduces the 15 amount of circuit analysis and synthesis involved in designing an n-order filter.
Another very significant advantage results from the fact that the output voltage EA of the active network 12 is a function of the capacitor C It is clear from the transfer function G in equation ( 8) that by increasing the voltage EA the size of the capacitor C may be reduced while maintaining the same shunt current I, and 20 hence the same filter characteristics Thus, by designing the active network 12 to produce a maximum output voltage EA the capacitance and thus the size of the capacitor C can be reduced to a minimum.
Once the transfer function G has been so defined and the operating parameters of a desired filter, such as the break frequency and damping ratios, are 25 set forth, it is a straightforward process, using conventional network synthesis techniques, to develop an electronic circuit for implementing the filter This process will be illustrated for both a first and a second order filter incorporating an n-1 active network 12 having the transfer equation ( 8).
Assuming, first, that a first order (n=l) filter is desired with a break frequency, 30 f.= 100 Hz, the transfer function G of equation ( 8) becomes:
G = ( 9) AE lA-RLCl where the filter polynomial coefficient A S equal to or 1 59 ( 10-3) seconds Further, specifying a value of 200 ohms for the load resistor 35 R, and maximum values for the active network voltage EA of 15 volts and of the filter output voltage E of 2 volts, the transfer function G becomes:
1,568,691 5 EA 15 1 59 ( 10-3)-200 C G= = ( 10) E 2 200 C which results in a value of C of 94 Jf.
The techniques of actually synthesizing a circuit from a transfer function are well-known in the art and are set forth in many standard texts such as Introduction to Modern Network Synthesis by M E Valkenburg, and Network Synthesis by D F 5 Tuttle There are a large number of circuits that can be used to satisfy the requirements for a particular active network and it is often most convenient to select one from a circuit handbook such as the Operational Amplifiers Design and Application published by the McGraw Hill Such a circuit utilizing operational amplifiers for implementing first order operation is illustrated in Figure 2 In the 10 circuit of Figure 2 the first order filter includes an operational amplifier 20 having its positive terminal connected to ground by means of line 16 Since G in this case is equal to 7 5, the amplifier 20 is connected in an inverting mode with a closed loop gain of 7 5 The dashed lines 12 in Figure 2 correspond to the active network 12 of Figure l and R, and C correspond to Z and C of Figure 1 along with lines 13, 14, 16 15 and 18 As computed above, C has a value of 94,uf and the load resistor R, is equal to 200 ohms The resistor 22 has a value of 100 K ohms and the feedback resistor 24 has a value of 750 K ohms The first order filter of Figure 2 also includes capacitor C, in order to achieve complete capacitive coupling of the active network 12 It is preferred that the value of C, be selected to maintain the input impedance to the 20 active network at a very high level.
A second order (n= 2) filter is illustrated in Figure 3 with the elements corresponding to the elements in Figure 1 having the same reference numerals For purposes of this example, the load resistance R, is 350 ohms and the desired filter characteristic includes a 25 on fn 30 Hz 2 nr and a damping ratio of 55 The transfer function G of equation ( 8) becomes:
GA-RLC FA 2 ( 11) RLC LA-RLC I where the filter polynomial coefficients 1 A 2 = = 2 81 ( 10-5) 30 Con 2 and 28 A= 5 84 ( 10-3).
con Combining equations ( 8) and ( 2) to get an expression that defines the value of EA for a second order filter results in:
F AGR Ll -RLC ( 12) 35 A G Eo=I TRL RLC C A 2 S + AS + 1 Assuming a peak value of 8 5 ma for IT the value of EA will peak whenever the term M, as defined below, is at its maximum value M is the Laplace portion of equation ( 12).
6 1,568,691 6 M = 7 A -RLC S+ 1 S jw ( 13) A 252 + AS + 1 By considering C to be very small and ignoring it, the term M can be evaluated over the frequency range of interest resulting in a maximum value of 1 3 at 25 Hz.
Then the value of C is approximated by solving the equations below for C:
EA (max) = IT (peak) ( ERLC) ( 14) 5 IT(peak) M A C ( 15) EA(max)+IT(peak) RL M giving C= 4 06 pf.
This value of C is substituted back into equation ( 13) above to get a second maximum value of M which turns out to be 1 46 at 25 Hz Utilizing this value for M in equation ( 14) results in a peak voltage for E, of 13 5 which is considered to be too 10 high for this particular application Therefore, the process is repeated by using the value of 1 46 for M to compute a new value of C in equation ( 15) resulting in a capacitance of 4 43,f Again using the new value for C, equation 14 is solved for the peak EA resulting in a peak voltage of 12 2 volts.
The iterative process described above can be used to compute a value for C to 15 the desired accuracy A circuit employing these values in a second order filter is provided in Figure 3 The load resistor RL has a value of 350 ohms and the capacitor C has a value of 4 43,uf as computed above Included is the operational amplifier 20 with its positive terminal connected through a 333 K ohm resistor 26 to the lower portion of the filter represented by line 13 The negative terminal of amplifier 20 is 20 connected through resistor 28, having a resistance of 499 K ohms, to the input line 14 Also shown in this embodiment is a capacitor C, which can be used capacitively to couple the active network, enclosed by dashed lines 12, to the input signal The active network 12 additionally includes a feedback network for the amplifier 20 which includes resistors 30 and 32, each having a value of 499 K ohms, and the 25 capacitor 34 having a capacitance of 016 gf.
Returning to the generalized concept of the n-order filter illustrated in Figure 1, the selection of a load impedance ZL of other than a pure resistance, as discussed above, will affect the transfer equation ( 1) of the active network 12 As an example of a second special case, the load impedance ZL illustrated in Figure 4 consists of a 30 load capacitor CL in parallel with the load resistor RL Here ZL will be equal to:
R, Ze= ( 16) RCLS+ I which results in transfer equation ( 1) becoming:
G _ A 1 D RLCLS 1 RLCS ( 17) E O CS RL RL RL G = {D 1-RL (C + CL) i ( 18) 35 7 1,568,691 7 Then by substituting in the filter polynomial for D, the transfer equation becomes:
n-2 A RL (C + CL) An Sn + An l S G =RLC A RL(C + CL) A RL( C + CL) A 25 + + 1 ( 19) A RL(C + CL) As a specific example of this second type of filter represented in Figure 4, assume a second order filter (n= 2) is desired where RL= 1000 ohms and CL=C=I uf 5 Here, the general filter characteristics will be represented by equation ( 2) having the value:
1,(l OO O Q) Eo ( 20) 52 285 -±+ 1 wn 2 con where the break frequency w,= 2 n( 10 Hz) and the damping constant 8 = 0 7 In this case D becomes: 10 52 2 ( 0 7)S D 2 + 1 ( 21) l 2 n( 10)l 2 27 r 10 where the filter polynomial coefficients A 2 = 2 53 ( 10-4) and A,= 022 Substituting these numerical values into the transfer function equation ( 19), G becomes:
022 1000 L 2 ( 10-6)7 2 53 ( 10-4)s + 1 ( 22) G = 1000 1 ( 10-6) 0203 G= 20 28 l 0125 + 1 l ( 23) 15 Thus, it is apparent that an active network having a first order response is required Such a circut is illustrated in Figure 5 Values for the various components of the active network are derived from the following relationships The current I, in line 14 is equal to:
E E, Ej-EA I=-= = Ej C 2 S+ ( 24) 20 R 1 R 2 R, By eliminating Ej and solving for EA/Eo the transfer equation G becomes:
2 R R 2 C 2 G = S + ( 25) R 1 2 Then by substituting the numerical values in equation ( 23) for the coefficients in equation ( 25) values for the circuit elements can be assigned Thus, by letting 5 R,= 100 KQ the value of R 2 can be determined, 2 R 2 = 20 giving R 2 =l MQ ( 26) R 1 and since R 2 C 2/2 = 0125, the value of C 2 will be 0125 uf.
Another significant feature of the filter of Figure 4 arises from the nature of the transfer function equation ( 19) By setting the portion A-Rj(C+CL) equal to zero, equation ( 19) becomes: 5 RL lAn Sn-2 + An 1 sn 3 + +A 2 ( 27) The implication of equation ( 27) is that when A-Rt(C+CL) is set to zero it is possible to implement the filter of Figure 4 by using a differentiating circuit element such as a capacitor, which corresponds to the S RC 10 term of equation ( 27), in combination with an n-2 order active network One particular advantage to this approach concerns the fact that it makes it significantly easier to synthesize the active network, since it has one less order.
As an example of this characteristic, a second order filter (n= 2) having the same performance specifications as the previously described filter in Figure 5 will 15 be disclosed Again, the filter will have a load resistance of R,= 1000 Q, a break frequency of c, = 2 r( 10 Hz), and a damping constant of 6 = 0 7 Here, the general filter characteristic equation ( 2) will be equal to:
IT( 1000 n) Eo ( 28) 52 2 ( 7)S + + 1 ( 2 n O 10)2 2 X 10 where the filter polynomial coefficients are: A= 2 53 ( 10-4) and A= 022 Since 20 A-RL(C+C) equals zero, the values of C and C, if selected to be equal will be:
A= 1000 (C+C,)= 022 ( 29) C+CL= 22 ( 10-6) ( 30) C=C,= 1 /ufd ( 31) The transfer equation ( 27) thus becomes: 25 1 G l 2 53 ( 10-4)Sl ( 32) ( 1000)( 1 1)( 10-6) A circuit which implements the second order filter with an active network having this transfer characteristic is shown in Figure 6 The differentiating circuit element is represented by a capacitor CD and the active network is enclosed within the dashed lines 12 The value of the capacitor CD is selected to be very small in 30 relation to C and C, so as to minimize the current flow to the operational amplifier Selecting a value of 011 uf for CD the value of the operational amplifier’s feedback resistor R 1 is determined by: the transfer function G of the combined differentiating element CD and the active network 12 which is:
G=R 1 CDS= 023 S ( 33) 35 Thus, the value of resistor R, is 2 09 MP.
1.568691 R An example of a third order (n= 3) filter based on this concept of using a differenting element shall also be discussed In a third order filter the transfer equation ( 27) becomes:
S G= lA 3 S+A 21 ( 34) RLC and the filter characteristic equation ( 2) becomes: 5 ITRL ES + 1)( 52 2 S + ( 35) 2 /+n + __ +n Using the same filter characteristics as in the previous examples, equation ( 35) takes on the value:
IT( 1000 n) E ( 36) 53 2 ( 7)52 S + + + 1 ( 2 x 10)3 ( 2 N 10)2 ( 27 r 10) 1000 IT Eo ( 37) 10 4.03 ( 10-«)53 + 6 08 ( 10-4)52 + 0385 + 1 where the filter polynomial coefficients are:
A 3 = 4 03 ( 10-6) ( 38) A 2 = 6 08 ( 10-4) ( 39) A=.038 ( 40) Since A-RL(C+CL) equals zero, 15 A=RL(C+CL)= 038 ( 41) Thus, by setting C=CL they will each have a value of 19 pfd This will produce transfer equation ( 34) having the value:
1000 ( 10) 19),( 10) q tl O tll 4 O 3 ( 10-6)S+ 6 O 8 ( 10-4) ( 42) G= 0032 Sl 0066 S+ 11 l ( 43) 20 A circuit for implementing this filter is illustrated in Figure 7 where a capacitor CD serves as the differentiating element and the active network including an operational amplifier 20 is enclosed by the dashed lines 12 The transfer function ( 43) is equal to:
SlR 1 C 1 G= 2 R 1 CDS l 2 S + 1 ( 44) 25 Thus, by selecting an appropriate capacitance for CD with the value of 1 pf, the values of R, and C 1 are determined as follows:
11 lll, Il 1,568,691 0032 R.= = 16000 Q ( 45) 2 C, 2 l 4 03 ( 10-6)1 C, 825,ufd ( 46) R, It is therefore apparent that there are a number of very significant advantages in utilizing an n-1 order active network in an n-order filter from the standpoint of the significantly reduced requirements for circuit elements and the simplification 5 of the design and synthesis of filters with predetermined performance characteristics Also, the use of a differentiating circuit element in connection with the active network to reduce the order of the active network provides further advantages in simplifying the design process.
Another advantage of the filter concept disclosed herein relates to the 10 characteristics of the operational amplifier 20 which forms the central element in the active network The fact that both the positive and negative terminals of the operational amplifier 20 are maintained at the same potential allows a virtual ground approach to the filter design An example of such a filter circuit is provided in Figure 8 The circuit in Figure 8 is operationally equivalent to the circuit in 15 Figure 7, the only difference being that the capacitor CA of Figure 8 functionally takes the place of the capacitors C, and C, of Figure 7 This is possible because the negative terminal of the operational amplifier 20 is maintained at the same potential as the positive terminal, thus in effect providing the same electrical characteristics as if capacitor CA were connected to line 13 The values for the 20 circuit elements in the filter of Figure 8 can be computed in essentially the same manner as they were for the filter of Figure 7 Here, for example, the value of resistors R, are:
2 RCA= 0032 ( 47) where CA is equal to 19,ufd Therefore, the resistance of each R, is equal to 84 2 Q 25 Also, since RC, _=.0066 ( 48) C 1 will have a value of 157,ufd Thus, it is apparent that by using the characteristics of the operational amplifier 20 the number of capacitors can be reduced, thereby further simplifying the filter circuit 30 It should be noted also that the basic concept of the n-order filter shown in Figure 1 is equally applicable to a filter connected to a voltage source E, with the load resistor RL in series as illustrated in Figure 9 or in a filter with a current I, output as shown in Figure 10.

Claims (1)

WHAT WE CLAIM IS: 35
1 An n-order active shunt filter (as herein defined), being a twoterminal network for passing a shunt filter current through the network when an input signal from a signal source is applied to the terminals; the filter comprising an n-1 order active network (as herein defined) having an input terminal connected to a first terminal of the 2-terminal network, a reference terminal connected to the second 40 terminal of the 2-terminal network, and an output terminal; and a capacitor C operatively connected between the first terminal of the 2-terminal network and the output terminal of the active network, wherein the shunt filter current is through the capacitor C.
2 A filter according to Claim 1 for receiving an input signal from a signal 45 source that includes a load impedance Z having a load resistance RL, wherein the n-1 order active network has a transfer function G defined by the equation:
EA 1 _ 1 G = -E CS R 1 ZL 1,568,691 10wherein EA is the output voltage of the active network, E is the output voltage of the filter, and D represents that portion of the filter characteristic which can be represented by the Laplace filter polynomial, An Sn+An Sn-‘+ +AS+I, where S in the Laplace operator and 5 An, An A are the filter polynominal coefficients.
3 A filter according to Claim 1 or Claim 2, wherein the n-I order active network is capacitively coupled to the terminals of the 2-terminal network.
4 A filter according to Claim 2, wherein the transfer function G of the n1 10 order active network is defined by the equation L ARLC 1 lA N n + A n-1 n-2 A 2 S+i l =RLC A-RLC A-RLC A-RC A filter according to any preceding claim, wherein n=l and the n-I order active network comprises an operational amplifier having a negative input terminal connected via a resistor to the first terminal of the two terminal network to receive 15 the input signal therefrom, a resistive feedback network connecting the output terminal of the operational amplifier with its negative input terminal, and means operatively connecting the output terminal of the operational amplifier to the capacitor C.
6 A filter according to any of Claims 1 to 4, wherein n= 2 and the n-1 order 20 active network comprises an operational amplifier having a negative input terminal connected via a resistor to the first terminal of the 2-terminal network to receive the input signal therefrom; means, including a resistor, connecting the positive input terminal of the operational amplifier to the second terminal of the 2-terminal network; a feedback network, including a grounded capacitor operatively 25 connected between two resistors, connecting the output terminal of the operational amplifier to its negative input terminal; and means operatively connecting the output terminal of the operational amplifier to the capacitor C.
7 A filter according to any of Claims 1 to 3, wherein n= 2 and the n-1 order active network comprises an operational amplifier having a negative input terminal 30 connected via a resistor to the first terminal of the 2-terminal network to receive the input signal therefrom; means connecting the positive input terminal of the operational amplifier to the second terminal of the 2-terminal network, a feedback network, including a grounded capacitor operatively connected between two resistors, connecting the output terminal of the operational amplifier to its negative 35 input terminal; and means operatively connecting the output terminal of the operational amplifier to the capacitor C.
8 A filter according to Claim 2, wherein the values of A, ZL and C are such that the transfer function G of the n-1 order active network is defined by the equation 40 S G= lAn Sn-2 +An-,Sn-3 + +A 2 l RC 9 A filter according to Claim 8, wherein the n-1 order active network comprises a differentiating circuit operatively connected to the first terminal of the 2-terminal network; and an n-2 order active network operatively connected to the differentiating circuit 45 A filter according to Claim 9, wherein the differentiating circuit comprises a capacitor CD operatively connected between the first terminal of the 2terminal network and the n-2 order active network.
11 A filter according to Claim 10, wherein n= 2 and the n-2 order active network comprises an operational amplifier operatively connected to the capacitor 50 CD; a resistive feedback network connecting the output of the operational amplifier with an input terminal of the operational amplifier; and means operatively connecting the output of the operational amplifier to the capacitor C.
I 1,568,691 1 1 1 1 12 A filter according to Claim 10, wherein n= 3 and the n-2 order active network comprises an operational amplifier operatively connected to the capacitor CD; a feedback network, including a grounded capacitor operatively connected between two resistors, connecting the output terminal of the operational amplifier to one of its input terminals; and means operatively connecting the output of the 5 operational amplifier to the capacitor C.
13 A filter according to Claim 9, wherein the load impedance of the signal source is a simple resistance; the differentiating circuit comprises a capacitor CA operatively connected between the first terminal of the 2-terminal network and the n-2 order active network; and the n-2 order active network comprises an 10 operational amplifier operatively connected to the capacitor CA and having substantially the same potential on each input terminal; a feedback network, including a grounded capacitor operatively connected between two resistors, connecting the output terminal of the operational amplifier to one of its input terminals; and means operatively connecting the output of the operational 15 amplifier to the capacitor C.
14 An n-order active shunt filter substantially as particularly described herein with reference to any of the drawings.
SERJEANTS, Chartered Patent Agents, The Crescent, Leicester.
Printed for Her Majesty’s Stationery Office, by the Courier Press, Leamington Spa 1980 Published by The Patent Office, 25 Southampton Buildings, London, WC 2 A IAY, from which copies may be obtained.
1,568,691

GB43843/76A
1975-11-03
1976-10-22
Electronic filter circuit

Expired

GB1568691A
(en)

Applications Claiming Priority (1)

Application Number
Priority Date
Filing Date
Title

US05/624,806

US4078205A
(en)

1975-11-03
1975-11-03
Electronic filter circuit

Publications (1)

Publication Number
Publication Date

GB1568691A
true

GB1568691A
(en)

1980-06-04

Family
ID=24503384
Family Applications (1)

Application Number
Title
Priority Date
Filing Date

GB43843/76A
Expired

GB1568691A
(en)

1975-11-03
1976-10-22
Electronic filter circuit

Country Status (8)

Country
Link

US
(1)

US4078205A
(en)

JP
(1)

JPS5284940A
(en)

CA
(1)

CA1070783A
(en)

DE
(1)

DE2647981C3
(en)

FR
(1)

FR2330204A1
(en)

GB
(1)

GB1568691A
(en)

IT
(1)

IT1123029B
(en)

SE
(1)

SE421365B
(en)

Families Citing this family (10)

* Cited by examiner, † Cited by third party

Publication number
Priority date
Publication date
Assignee
Title

US4896351A
(en)

1985-06-27
1990-01-23
Siemens Ag
Apparatus for separating dc current and ac current components of a composite signal

JPS63119312A
(en)

1986-06-25
1988-05-24
Nippon Columbia Co Ltd
Frequency characteristic correcting circuit

US4831377A
(en)

1987-04-30
1989-05-16
Hewlett-Packard Company
Method and apparatus for reduced settling time in a filter for a DC voltage

FR2627335B1
(en)

1988-02-16
1990-07-20
Sgs Thomson Microelectronics

CIRCUIT FOR COMPENSATING FOR THE ATTENUATION OF A BAND-CUTTING FILTER AT FREQUENCIES LESS THAN ITS CUTTING FREQUENCY

FR2630600A1
(en)

1988-04-22
1989-10-27
Labo Electronique Physique

ACTIVE CIRCUIT FOR HIGH AND HYPER FREQUENCIES

AU2001282963A1
(en)

2000-07-21
2002-02-05
Ixys Corporation
Active power filter for isolating electrically noisy load from low noise power supply

EP1758248B1
(en)

2005-08-22
2009-06-10
Infineon Technologies AG
Circuit and method for filtering a radio frequency signal

WO2007119264A1
(en)

2006-03-20
2007-10-25
Fujitsu Limited
Input impedance circuit and low-pass filter circuit

KR100881918B1
(en)

2007-06-07
2009-02-06
삼성전자주식회사
High order low pass filtering circuit and method using the same

US20160087602A1
(en)

2014-09-24
2016-03-24
Western Digital Technologies, Inc.
Adaptive feedback for power distribution network impedance barrier suppression

Family Cites Families (5)

* Cited by examiner, † Cited by third party

Publication number
Priority date
Publication date
Assignee
Title

US3564441A
(en)

1968-03-04
1971-02-16
United Control Corp
Low-pass active filter

CA887822A
(en)

1968-07-13
1971-12-07
Szabo John
Active filters

US3702405A
(en)

1971-11-17
1972-11-07
Us Air Force
Electronically variable capacitance

GB1413722A
(en)

1973-01-17
1975-11-12
Post Office
Filter networks

GB1413721A
(en)

1973-01-17
1975-11-12
Post Office
Subnetworks for filter ladder networks

1975

1975-11-03
US
US05/624,806
patent/US4078205A/en
not_active
Expired – Lifetime

1976

1976-10-21
JP
JP12556676A
patent/JPS5284940A/en
active
Granted

1976-10-21
FR
FR7631789A
patent/FR2330204A1/en
active
Granted

1976-10-22
CA
CA264,582A
patent/CA1070783A/en
not_active
Expired

1976-10-22
GB
GB43843/76A
patent/GB1568691A/en
not_active
Expired

1976-10-22
DE
DE2647981A
patent/DE2647981C3/en
not_active
Expired

1976-10-28
SE
SE7611979A
patent/SE421365B/en
not_active
IP Right Cessation

1976-11-03
IT
IT52017/76A
patent/IT1123029B/en
active

Also Published As

Publication number
Publication date

FR2330204B1
(en)

1982-11-19

CA1070783A
(en)

1980-01-29

SE421365B
(en)

1981-12-14

IT1123029B
(en)

1986-04-30

DE2647981C3
(en)

1980-01-03

JPS576725B2
(en)

1982-02-06

FR2330204A1
(en)

1977-05-27

US4078205A
(en)

1978-03-07

SE7611979L
(en)

1977-05-04

JPS5284940A
(en)

1977-07-14

DE2647981A1
(en)

1977-05-18

DE2647981B2
(en)

1979-05-17

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